Source and load circuit impedance
In electronics, impedance matching is the practice of designing the input impedance of an electrical load or the output impedance of its corresponding signal source to maximize the power transfer or minimize signal reflection from the load.
In the case of a complex source impedance Z_{S} and load impedance Z_{L}, maximum power transfer is obtained when

Z_\mathrm S = Z_\mathrm L^* \,
where the asterisk indicates the complex conjugate of the variable. Where Z_{S} represents the characteristic impedance of a transmission line, minimum reflection is obtained when

Z_\mathrm S = Z_\mathrm L \,
The concept of impedance matching found first applications in electrical engineering, but is relevant in other applications in which a form of energy, not necessarily electrical, is transferred between a source and a load. An alternative to impedance matching is impedance bridging, in which the load impedance is chosen to be much larger than the source impedance and maximizing voltage transfer, rather than power, is the goal.
Contents

Theory 1

Reflectionless matching 1.1

Maximum power transfer matching 1.2

Power transfer 2

Impedancematching devices 3

Transformers 3.1

Resistive network 3.2

Stepped transmission line 3.3

Filters 3.4

Power factor correction 4

Transmission lines 5

Singlesource transmission line driving a load 5.1

Loadend conditions 5.1.1

Sourceend conditions 5.1.2

Sourceend impedance 5.1.2.1

Transfer function 5.1.2.2

Electrical examples 6

Telephone systems 6.1

Loudspeaker amplifiers 6.2

Nonelectrical examples 7

Acoustics 7.1

Optics 7.2

Mechanics 7.3

See also 8

Notes 9

References 10

External links 11
Theory
Impedance is the opposition by a system to the flow of energy from a source. For constant signals, this impedance can also be constant. For varying signals, it usually changes with frequency. The energy involved can be electrical, mechanical, magnetic or thermal. The concept of electrical impedance is perhaps the most commonly known. Electrical impedance, like electrical resistance, is measured in ohms. In general, impedance has a complex value; this means that loads generally have a resistance component (symbol: R) which forms the real part of Z and a reactance component (symbol: X) which forms the imaginary part of Z.
In simple cases (such as lowfrequency or directcurrent power transmission) the reactance may be negligible or zero; the impedance can be considered a pure resistance, expressed as a real number. In the following summary we will consider the general case when resistance and reactance are both significant, and the special case in which the reactance is negligible.
Reflectionless matching
Impedance matching to minimize reflections is achieved by making the load impedance equal to the source impedance. If the source impedance, load impedance and transmission line characteristic impedance are purely resistive, then reflectionless matching is the same as maximum power transfer matching.^{[1]}
Maximum power transfer matching
Complex conjugate matching is used when maximum power transfer is required, namely

Z_\mathsf{load} = Z_\mathsf{source}^* \,
where * indicates the complex conjugate. This differs from reflectionless matching only when the source or load have a reactive component.
If the source has a reactive component, but the load is purely resistive, then matching can be achieved by adding a reactance of the same magnitude but opposite sign to the load. This simple matching network, consisting of a single element, will usually only achieve a perfect match at a single frequency. This is because the added element will either be a capacitor or an inductor, whose impedance in both cases is frequency dependent, and will not, in general, follow the frequency dependence of the source impedance. For wide bandwidth applications, a more complex network must be designed.
Power transfer
Whenever a source of power with a fixed output impedance such as an electric signal source, a radio transmitter or a mechanical sound (e.g., a loudspeaker) operates into a load, the maximum possible power is delivered to the load when the impedance of the load (load impedance or input impedance) is equal to the complex conjugate of the impedance of the source (that is, its internal impedance or output impedance). For two impedances to be complex conjugates their resistances must be equal, and their reactances must be equal in magnitude but of opposite signs. In lowfrequency or DC systems (or systems with purely resistive sources and loads) the reactances are zero, or small enough to be ignored. In this case, maximum power transfer occurs when the resistance of the load is equal to the resistance of the source (see maximum power theorem for a mathematical proof).
Impedance matching is not always necessary. For example, if a source with a low impedance is connected to a load with a high impedance the power that can pass through the connection is limited by the higher impedance. This maximumvoltage connection is a common configuration called impedance bridging or voltage bridging, and is widely used in signal processing. In such applications, delivering a high voltage (to minimize signal degradation during transmission or to consume less power by reducing currents) is often more important than maximum power transfer.
In older audio systems (reliant on transformers and passive filter networks, and based on the telephone system), the source and load resistances were matched at 600 ohms. One reason for this was to maximize power transfer, as there were no amplifiers available that could restore lost signal. Another reason was to ensure correct operation of the hybrid transformers used at central exchange equipment to separate outgoing from incoming speech, so these could be amplified or fed to a fourwire circuit. Most modern audio circuits, on the other hand, use active amplification and filtering and can use voltagebridging connections for greatest accuracy. Strictly speaking, impedance matching only applies when both source and load devices are linear; however, matching may be obtained between nonlinear devices within certain operating ranges.
Impedancematching devices
Adjusting the source impedance or the load impedance, in general, is called "impedance matching". There are three ways to improve an impedance mismatch, all of which are called "impedance matching":

Devices intended to present an apparent load to the source of Z_{load} = Z_{source}* (complex conjugate matching). Given a source with a fixed voltage and fixed source impedance, the maximum power theorem says this is the only way to extract the maximum power from the source.

Devices intended to present an apparent load of Z_{load} = Z_{line} (complex impedance matching), to avoid echoes. Given a transmission line source with a fixed source impedance, this "reflectionless impedance matching" at the end of the transmission line is the only way to avoid reflecting echoes back to the transmission line.

Devices intended to present an apparent source resistance as close to zero as possible, or presenting an apparent source voltage as high as possible. This is the only way to maximize energy efficiency, and so it is used at the beginning of electrical power lines. Such an impedance bridging connection also minimizes distortion and electromagnetic interference; it is also used in modern audio amplifiers and signalprocessing devices.
There are a variety of devices used between a source of energy and a load that perform "impedance matching". To match electrical impedances, engineers use combinations of transformers, resistors, inductors, capacitors and transmission lines. These passive (and active) impedancematching devices are optimized for different applications and include baluns, antenna tuners (sometimes called ATUs or rollercoasters, because of their appearance), acoustic horns, matching networks, and terminators.
Transformers
Transformers are sometimes used to match the impedances of circuits. A transformer converts alternating current at one voltage to the same waveform at another voltage. The power input to the transformer and output from the transformer is the same (except for conversion losses). The side with the lower voltage is at low impedance (because this has the lower number of turns), and the side with the higher voltage is at a higher impedance (as it has more turns in its coil).
One example of this method involves a television balun transformer. This transformer converts a balanced signal from the antenna (via 300ohm twinlead) into an unbalanced signal (75ohm coaxial cable such as RG6). To match the impedances of both devices, both cables must be connected to a matching transformer with a turns ratio of 2 (such as a 2:1 transformer). In this example, the 75ohm cable is connected to the transformer side with fewer turns; the 300ohm line is connected to the transformer side with more turns. The formula for calculating the transformer turns ratio for this example is:

\text{turns ratio} = \sqrt{\frac{\text{source resistance}}{\text{load resistance}}}
Resistive network
Resistive impedance matches are easiest to design and can be achieved with a simple L pad consisting of two resistors. Power loss is an unavoidable consequence of using resistive networks, and they are only (usually) used to transfer line level signals.
Stepped transmission line
Most lumpedelement devices can match a specific range of load impedances. For example, in order to match an inductive load into a real impedance, a capacitor needs to be used. If the load impedance becomes capacitive, the matching element must be replaced by an inductor. In many cases, there is a need to use the same circuit to match a broad range of load impedance and thus simplify the circuit design. This issue was addressed by the stepped transmission line,^{[2]} where multiple, serially placed, quarterwave dielectric slugs are used to vary a transmission line's characteristic impedance. By controlling the position of each element, a broad range of load impedances can be matched without having to reconnect the circuit.
Filters
Filters are frequently used to achieve impedance matching in telecommunications and radio engineering. In general, it is not theoretically possible to achieve perfect impedance matching at all frequencies with a network of discrete components. Impedance matching networks are designed with a definite bandwidth, take the form of a filter, and use filter theory in their design.
Applications requiring only a narrow bandwidth, such as radio tuners and transmitters, might use a simple tuned filter such as a stub. This would provide a perfect match at one specific frequency only. Wide bandwidth matching requires filters with multiple sections.
Lsection
L networks for narrowband matching a source or load impedance
Z to a transmission line with characteristic impedance
Z_{0}.
X and
B may each be either positive (inductor) or negative (capacitor). If
Z/
Z_{0} is inside the 1+jx circle on the
Smith chart (i.e. if
Re(Z/Z_{0})>1), network (a) can be used; otherwise network (b) can be used.
^{[3]}
A simple electrical impedancematching network requires one capacitor and one inductor. One reactance is in parallel with the source (or load), and the other is in series with the load (or source). If a reactance is in parallel with the source, the effective network matches from high to low impedance. The Lsection is inherently a narrowband matching network.
The analysis is as follows. Consider a real source impedance of R_1 and real load impedance of R_2. If a reactance X_1 is in parallel with the source impedance, the combined impedance can be written as:

\frac{j R_1 X_1}{R_1 + j X_1}
If the imaginary part of the above impedance is canceled by the series reactance, the real part is

R_2 = \frac{R_1 X_1^2}{R_1^2 + X_1^2}
Solving for X_1

X_1 = \sqrt{\frac{R_2 R_1^2}{R_1  R_2}}
If R_1 \gg R_2 the above equation can be approximated as

X_1 \approx \sqrt{R_1 R_2} \,
The inverse connection (impedance stepup) is simply the reverse—for example, reactance in series with the source. The magnitude of the impedance ratio is limited by reactance losses such as the Q of the inductor. Multiple Lsections can be wired in cascade to achieve higher impedance ratios or greater bandwidth. Transmission line matching networks can be modeled as infinitely many Lsections wired in cascade. Optimal matching circuits can be designed for a particular system using Smith charts.
Power factor correction
Power factor correction devices are intended to cancel the reactive and nonlinear characteristics of a load at the end of a power line. This causes the load seen by the power line to be purely resistive. For a given true power required by a load this minimizes the true current supplied through the power lines, and minimizes power wasted in the resistance of those power lines. For example, a maximum power point tracker is used to extract the maximum power from a solar panel and efficiently transfer it to batteries, the power grid or other loads. The maximum power theorem applies to its "upstream" connection to the solar panel, so it emulates a load resistance equal to the solar panel source resistance. However, the maximum power theorem does not apply to its "downstream" connection. That connection is an impedance bridging connection; it emulates a highvoltage, lowresistance source to maximize efficiency.
On the power grid the overall load is usually inductive. Consequently, power factor correction is most commonly achieved with banks of capacitors. It is only necessary for correction to be achieved at one single frequency, the frequency of the supply. Complex networks are only required when a band of frequencies must be matched and this is the reason why simple capacitors are all that is usually required for power factor correction.
Transmission lines
Coaxial transmission line with one source and one load
Impedance bridging is unsuitable for RF connections, because it causes power to be reflected back to the source from the boundary between the high and the low impedances. The reflection creates a standing wave if there is reflection at both ends of the transmission line, which leads to further power waste and may cause frequencydependent loss. In these systems, impedance matching is desirable.
In electrical systems involving transmission lines (such as radio and fiber optics)—where the length of the line is long compared to the wavelength of the signal (the signal changes rapidly compared to the time it takes to travel from source to load)— the impedances at each end of the line must be matched to the transmission line's characteristic impedance (Z_c) to prevent reflections of the signal at the ends of the line. (When the length of the line is short compared to the wavelength, impedance mismatch is the basis of transmissionline impedance transformers; see previous section.) In radiofrequency (RF) systems, a common value for source and load impedances is 50 ohms. A typical RF load is a quarterwave ground plane antenna (37 ohms with an ideal ground plane; it can be matched to 50 ohms by using a modified ground plane or a coaxial matching section, i.e., part or all the feeder of higher impedance).
The general form of the voltage reflection coefficient for a wave moving from medium 1 to medium 2 is given by

\Gamma_{12} = {Z_2  Z_1 \over Z_2 + Z_1}
while the voltage reflection coefficient for a wave moving from medium 2 to medium 1 is

\Gamma_{21} = {Z_1  Z_2 \over Z_1 + Z_2}

\Gamma_{21} = \Gamma_{12} \,
so the reflection coefficient is the same (except for sign), no matter from which direction the wave approaches the boundary.
There is also a current reflection coefficient; it is the same as the voltage coefficient, except that it has an opposite sign. If the wave encounters an open at the load end, positive voltage and negative current pulses are transmitted back toward the source (negative current means the current is going the opposite direction). Thus, at each boundary there are four reflection coefficients (voltage and current on one side, and voltage and current on the other side). All four are the same, except that two are positive and two are negative. The voltage reflection coefficient and current reflection coefficient on the same side have opposite signs. Voltage reflection coefficients on opposite sides of the boundary have opposite signs.
Because they are all the same except for sign it is traditional to interpret the reflection coefficient as the voltage reflection coefficient (unless otherwise indicated). Either end (or both ends) of a transmission line can be a source or a load (or both), so there is no inherent preference for which side of the boundary is medium 1 and which side is medium 2. With a single transmission line it is customary to define the voltage reflection coefficient for a wave incident on the boundary from the transmission line side, regardless of whether a source or load is connected on the other side.
Singlesource transmission line driving a load
Loadend conditions
In a transmission line, a wave travels from the source along the line. Suppose the wave hits a boundary (an abrupt change in impedance). Some of the wave is reflected back, while some keeps moving onwards. (Assume there is only one boundary, at the load.)
Let

V_i \, and I_i \, be the voltage and current that is incident on the boundary from the source side.

V_t \, and I_t \, be the voltage and current that is transmitted to the load.

V_r \, and I_r \, be the voltage and current that is reflected back toward the source.
On the line side of the boundary V_i = Z_c I_i \, and V_r = Z_c I_r \, and on the load side V_t = Z_L I_t \, where V_i \, , V_r \, , V_t \, , I_i \, , I_r \, , I_t \, , and Z_c \, are phasors.
At a boundary, voltage and current must be continuous, therefore

V_t = V_i + V_r \,

I_t = I_i + I_r \,
All these conditions are satisfied by

V_r = \Gamma_{TL} V_i \,

I_r =  \Gamma_{TL} I_i \,

V_t = (1 + \Gamma_{TL} ) V_i \,

I_t = ( 1  \Gamma_{TL} ) I_i \,
where \Gamma_{TL} \, the reflection coefficient going from the transmission line to the load.

\Gamma_{TL} = {Z_L  Z_c \over Z_L + Z_c} = \Gamma_L \, ^{[4]}^{[5]}^{[6]}
The purpose of a transmission line is to get the maximum amount of energy to the other end of the line (or to transmit information with minimal error), so the reflection is as small as possible. This is achieved by matching the impedances Z_L and Z_c so that they are equal (\Gamma = 0).
Sourceend conditions
At the source end of the transmission line, there may be waves incident both from the source and from the line; a reflection coefficient for each direction may be computed with

 \Gamma_{ST} = \Gamma_{TS} = {Z_s  Z_c \over Z_s + Z_c} = \Gamma_S \, ,
where Zs is the source impedance. The source of waves incident from the line are the reflections from the load end. If the source impedance matches the line, reflections from the load end will be absorbed at the source end. If the transmission line is not matched at both ends reflections from the load will be rereflected at the source and rerereflected at the load end ad infinitum, losing energy on each transit of the transmission line. This can cause a resonance condition and strongly frequencydependent behavior. In a narrowband system this can be desirable for matching, but is generally undesirable in a wideband system.
Sourceend impedance

Z_{in} = Z_C \frac { (1 + T^2 \Gamma_L ) } {( 1  T^2 \Gamma_L )} \, ^{[7]}
where T \ , is the oneway transfer function (from either end to the other) when the transmission line is exactly matched at source and load. T \, accounts for everything that happens to the signal in transit (including delay, attenuation and dispersion). If there is a perfect match at the load, \Gamma_L = 0 \, and Z_{in} = Z_C \,
Transfer function

V_L = V_S \frac {T (1  \Gamma_S)(1 + \Gamma_L)} { 2 ( 1 T^2 \Gamma_S \Gamma_L) } \,
where V_S \, is the open circuit (or unloaded) output voltage from the source.
Note that if there is a perfect match at both ends

\Gamma_L = 0 \, and \Gamma_S = 0 \,
and then

V_L = V_S \frac {T} {2}\, .
Electrical examples
Telephone systems
Telephone systems also use matched impedances to minimise echo on longdistance lines. This is related to transmissionline theory. Matching also enables the telephone hybrid coil (2 to 4wire conversion) to operate correctly. As the signals are sent and received on the same twowire circuit to the central office (or exchange), cancellation is necessary at the telephone earpiece so excessive sidetone is not heard. All devices used in telephone signal paths are generally dependent on matched cable, source and load impedances. In the local loop, the impedance chosen is 600 ohms (nominal). Terminating networks are installed at the exchange to offer the best match to their subscriber lines. Each country has its own standard for these networks, but they are all designed to approximate about 600 ohms over the voice frequency band.
Loudspeaker amplifiers
Typical push–pull audio tube power amplifier, matched to loudspeaker with an impedancematching transformer
Audio amplifiers typically do not match impedances, but provide an output impedance that is lower than the load impedance (such as < 0.1 ohm in typical semiconductor amplifiers), for improved speaker damping. For vacuum tube amplifiers, impedancechanging transformers are often used to get a low output impedance, and to better match the amplifier's performance to the load impedance. Some tube amplifiers have output transformer taps to adapt the amplifier output to typical loudspeaker impedances.
The output transformer in vacuumtubebased amplifiers has two basic functions:

Separation of the AC component (which contains the audio signals) from the DC component (supplied by the power supply) in the anode circuit of a vacuumtubebased power stage. A loudspeaker should not be subjected to DC current.

Reducing the output impedance of power pentodes (such as the EL34) in a commoncathode configuration.
The impedance of the loudspeaker on the secondary coil of the transformer will be transformed to a higher impedance on the primary coil in the circuit of the power pentodes by the square of the turns ratio, which forms the impedance scaling factor.
The output stage in commondrain or commoncollector semiconductorbased end stages with MOSFETs or power transistors has a very low output impedance. If they are properly balanced, there is no need for a transformer or a large electrolytic capacitor to separate AC from DC current.
Nonelectrical examples
Acoustics
Similar to electrical transmission lines, an impedance matching problem exists when transferring sound energy from one medium to another. If the acoustic impedance of the two media are very different most sound energy will be reflected (or absorbed), rather than transferred across the border. The gel used in medical ultrasonography helps transfer acoustic energy from the transducer to the body and back again. Without the gel, the impedance mismatch in the transducertoair and the airtobody discontinuity reflects almost all the energy, leaving very little to go into the body.
The bones in the middle ear provide impedance matching between the eardrum (which is acted upon by vibrations in air) and the fluidfilled inner ear.
Horns are used like transformers, matching the impedance of the transducer to the impedance of the air. This principle is used in both horn loudspeakers and musical instruments. Most loudspeaker systems contain impedance matching mechanisms, especially for low frequencies. Because most driver impedances which are poorly matched to the impedance of free air at low frequencies (and because of outofphase cancellations between output from the front and rear of a speaker cone), loudspeaker enclosures both match impedances and prevent interference. Sound, coupling with air, from a loudspeaker is related to the ratio of the diameter of the speaker to the wavelength of the sound being reproduced. That is, larger speakers can produce lower frequencies at a higher level than smaller speakers for this reason. Elliptical speakers are a complex case, acting like large speakers lengthwise and small speakers crosswise. Acoustic impedance matching (or the lack of it) affects the operation of a megaphone, an echo and soundproofing.
Optics
A similar effect occurs when light (or any electromagnetic wave) hits the interface between two media with different refractive indices. For nonmagnetic materials, the refractive index is inversely proportional to the material's characteristic impedance. An optical or wave impedance (that depends on the propagation direction) can be calculated for each medium, and may be used in the transmissionline reflection equation

r = {Z_2  Z_1 \over Z_1 + Z_2}
to calculate reflection and transmission coefficients for the interface. For nonmagnetic dielectrics, this equation is equivalent to the Fresnel equations. Unwanted reflections can be reduced by the use of an antireflection optical coating.
Mechanics
If a body of mass m collides elastically with a second body, maximum energy transfer to the second body will occur when the second body has the same mass m. In a headon collision of equal masses, the energy of the first body will be completely transferred to the second body (as in Newton's cradle for example). In this case, the masses act as "mechanical impedances", which must be matched. If m_1 and m_2 are the masses of the moving and stationary bodies, and P is the momentum of the system (which remains constant throughout the collision), the energy of the second body after the collision will be E_{2}:

E_2=\frac{2P^2m_2}{(m_1+m_2)^2}
which is analogous to the powertransfer equation.
These principles are useful in the application of highly energetic materials (explosives). If an explosive charge is placed on a target, the sudden release of energy causes compression waves to propagate through the target radially from the pointcharge contact. When the compression waves reach areas of high acoustic impedance mismatch (such as the opposite side of the target), tension waves reflect back and create spalling. The greater the mismatch, the greater the effect of creasing and spalling will be. A charge initiated against a wall with air behind it will do more damage to the wall than a charge initiated against a wall with soil behind it.
See also
Notes

^ Stutzman & Thiele 2012, p. 177, page link

^ , vol. 199 issue 1 (July 2009), pp. 104110Journal of Magnetic ResonanceChunqui Qian and William W. Brey, "Impedance matching with an adjustable segmented transmission line". Retrieved 20111029.

^ Pozer, David. Microwave Engineering (3rd ed.). p. 223.

^ Kraus (1984, p. 407)

^ Sadiku (1989, pp. 505–507)

^ Hayt (1989, pp. 398–401)

^ Karakash (1950, pp. 52–57)
References

Floyd, Thomas (1997), Principles of Electric Circuits (5th ed.), Prentice Hall,

Hayt, William (1989), Engineering Electromagnetics (5th ed.), McGrawHill,

Karakash, John J. (1950), Transmission Lines and Filter Networks (1st ed.), Macmillan

Kraus, John D. (1984), Electromagnetics (3rd ed.), McGrawHill,

Sadiku, Matthew N. O. (1989), Elements of Electromagnetics (1st ed.), Saunders College Publishing,

Stutzman, Warren L.; Thiele, Gary (2012), Antenna Theory and Design, John Wiley & Sons,

Young, E.C., The Penguin Dictionary of Electronics, Penguin, ISBN 0140511873 (see 'maximum power theorem', 'impedance matching')
External links

Impedance Matching Impedance Matching with the Smith Chart for Antennas

Unity Gain and Impedance Matching

Impedance matching for microphones: Is it necessary? No.

Calculation: Damping of impedance matching  connecting Zout and Zin

Impedance matching: A primer

Tutorial on RF impedance matching using the Smith Chart

A description of impedance matching

Conjugate matching versus reflectionless matching  pdf

Impedance Matching Networks

Java applets demonstrating impedance mismatching

The impedance transformation along a stepped transmission line
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